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Start-Up Method of an Induction Motor Driven by a Modular Multilevel Cascade Inverter without Speed Sensor.
Mr. Sachin Ghule PG Student Gokhale Education Society's R. H.
Sapat College of Engineering, Management Studies & Research,
Nashik, India [email protected]
Prof. Deepak M.Sonje Asst.Profesor Gokhale Education Society's R. H.
Sapat College of Engineering, Management Studies & Research,
Nashik, India
[email protected] ABSTRACT
This paper presents hypothetical and trial exchanges on a handy speed-sensor less start-up strategy for an enlistment engine driven by a secluded multilevel course inverter in view of double-star chopper cells (MMCI-DSCC) from halt to middle speed. This engine drive is reasonable, especially for a vast limit fan-or blower-like load. The load torque is relative to a square of the engine mechanical speed. The start-up method is characterized by combining capacitor-voltage control with motor-speed control. The motor-speed control with the minimal stator current plays a crucial role in eliminating a speed sensor from the drive system and in reducing an ac voltage fluctuation occurring across each dc capacitor. Experimental results obtained from the 400-V 15- kW downscaled system with no speed sensor verify that the motor-speed control proposed for the DSCC-based drive system can enhance the start-up torque by a factor of three under the same ac-voltage fluctuation. Several start-up waveforms show stable performance from standstill to middle speed with different load torques.
Keywords
Total Harmonic Distortion,Cascade Multilevel Inverter, electromagnetic interference,modular multilevel cascaded inverter,Double star chopper cell
1. INTRODUCTION
Induction motors are the most widely used electrical motors due to their reliability, low cost and robustness. However, induction motors do not inherently have the capability of variable speed operation. Due to this reason, earlier dc motors were applied in most of the electrical drives. But the recent developments in speed control methods of the induction motor have led to their large scale use in almost all electrical drives.
The importance of multilevel inverters has been increased since last few decades. These new types of inverters are suitable for high voltage and high power application due to their ability to synthesize waveforms with better harmonic spectrum and with less Total Harmonic Distortion (THD).
Numerous topologies have been introduced and widely studied for utility of non-conventional sources and also for drive applications. Cascade Multilevel Inverter (CMLI) is more recent and popular type of power electronic converter that synthesizes a desired output voltage from several levels of dc voltages as inputs. If satisfactory number of dc sources is used, a nearly sinusoidal voltage waveform can be synthesized. CMLI offers several advantages such as, its capabilities to operate at high voltage with lower dv/dt per switching, high efficiency and low electromagnetic interference [EMI].The Proposed system is a MMCI (modular multilevel cascaded inverter) –DSCC (double star chopper cell) based induction motor drive, in which the motor starts
rotating from standstill to middle speed with a ramp change.
This motor drive is suitable, particularly for an application to a fan or blower-like load. This proposed motor-speed control of an induction motor is similar to the conventional “volts- per-hertz” and “slip-frequency” control techniques, but different in terms of combining the two control techniques together. The motor-speed control is based on “feedback”
control of the stator current, which is the same as that in the slip-frequency control, whereas the commands for the amplitude and frequency of the stator current are based on
“feed forward” control in consideration of a speed-versus- load-torque characteristic. Thus in this system, speed sensor is not required. Also, this motor-speed control technique can be applied to any inverter with current sensors at the ac terminals. The idea is to design and develop a Simulink model of a capacitor voltage control system to verify that it can be useful to eliminate ac-voltage fluctuation in all the frequency range.
2 . PROPOSED SYSTEM
2.1 Overall control block diagram for the start-up method.
Fig .1. Overall control block diagram
2.2.Capacitor-Voltage Control
The proposed system two kinds of existing capacitor-voltage control techniques for regulating the mean dc voltage of each dc capacitor and for mitigating the ac-voltage fluctuation at the stator-current frequency. Fig. 3.1 shows the overall control block diagram of the start-up method. The 24 dc-capacitor voltages VCjuvw, the dc-link voltage vdc, and the six arm currents iPuvw and iNuvw are detected and they are input signals
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for the block diagram. Note that the three stator currents iuvw
are calculated from the detected arm currents. The mean dc- voltage regulation can be achieved by using the “arm”
balancing control applied to the six arms and the “individual”
balancing control applied to the one arm at the same time. The ac-voltage fluctuation can be mitigated by the sophisticated control discussed. This control interact the common-mode voltage vcom, which is injected to three centre-tap terminals of the DSCC with the ac components of the three circulating currents ˜iZuvw. This can mitigate the ac voltage fluctuation at the stator-current frequency, thus leading to start up from standstill. As a result, the remaining ac-voltage fluctuations are independent of the time-varying frequencies of the stator current, but dependent on a fixed frequency of the injected common-mode voltage (50 Hz in this experiment). The circulating-current feedback control included in the mean dc voltage regulation block yields a command voltage of .Finally command u-phase voltages for each chopper cell (i.e. ) are given as follows:
(1)
(2)
Here, Va*
and V*Bju are used to regulate the mean dc voltage, V*u is the command motor voltage, V*com is the command common-mode voltage, and Vdc is the dc-link voltage used as feed-forward control. The command rms value of the common-mode voltage V*com should be set as high as possible to reduce the amplitude of each ac circulating current, because it is inversely proportional to Vcom. Moreover, there is no relationship between common-mode voltage and power rating of the motor. In proposed system, switches over the two capacitor-voltage control techniques according to the stator- current frequency as follows.
In a low-speed range of f≤12Hz, the rms value of the common-mode voltage Vcom and the ac circulating currents ˜iZuvw are controlled actively to mitigate the ac voltage fluctuation of each dc- capacitor voltage.
When f≥20 Hz, neither Vcom nor ˜iZuvw is superimposed, during a frequency range of 12≤f≤20Hz, vcom, and ˜i*Zuvw decrease linearly in their amplitude.
Note that the dc circulating current is used to regulate the mean dc voltage of each dc capacitor through all frequency range.
2.2 Circuit configuration for MMCI-DSCC
In this section we are going to discuss about configuration of proposed system, Fig. 2 (a) shows the main circuit configuration of the DSCC, Each leg consists of eight cascaded bidirectional chopper cells shown in Fig. 2 (b) and a centre tapped inductor per phase, as shown in Fig.2 (c). The centre tap of each inductor is connected directly to each of the stator terminals of an induction motor, where iu is the u-phase stator current. The centre-tapped inductor is more cost
effective than two non-coupled inductors per leg, because the centre tapped inductor presents inductance LZ only to the circulating current iZ and no inductance to the stator current iu. It brings significant reductions in size, weight, and cost of the magnetic core. These advantages in the centre-tapped inductor are mostly welcomed, particularly applications to motor drives, in which no ac inductors are required between the motor and the inverter. In Fig.3.2 (a) instantaneous currents iPu and iNu are the u phase positive and negative-arm currents, respectively, and iZu is the u-phase circulating current defined as follows:
Fig 2. - Circuit configuration for MMCI-DSCC.
(a) Power circuit. (b) Chopper cell. (c) Center- tapped inductor.
Note that iZu includes dc and ac components to be used for the capacitor-voltage control. The dc component flows from the common dc link to each leg, while the ac component circulates among the three legs. The individual ac components included in the three-phase circulating currents ˜iZu, ˜iZv, and
˜iZw cancel each other out, so that no ac component appears in either motor current or d c-link current.
The arm currents iPu (positive phase current) and iNu (Negative phase current) can be expressed as linear functions of two independent variables iu and iZu as follows:
(3) (4)
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The dc-capacitor voltage in each chopper cell consists of dc and ac components causing an AC-voltage fluctuation.
When neither common-mode voltage nor ac circulating current is superimposed, the peak-to-peak ac-voltage fluctuation ΔVCju is approximated as follows
(5)
Where I1 is the rms value of the stator current, f is the frequency of the stator current, and C is the capacitance value of each dc capacitor. According to, ΔvCju is inversely proportional to f and proportional to I1. Hence, ΔvCju increases as the stator-current frequency decreases. Increasing the ac- voltage fluctuation is undesirable due to the following reasons,
It affects the voltage rating of insulated- gate bipolar transistors.
It causes over-modulation to each chopper cell.
It makes the system unstable because the ac-voltage fluctuation can be considered as a disturbance to the control system.
Therefore, the ac-voltage fluctuation should be mitigated to an acceptable level.
2.3 Motor-Speed Control
This section describes a motor-speed control forming a feedback loop of three-phase stator currents for achieving a stable start-up of an induction motor. First, the motor-speed control is discussed in terms of a form and function. Second, it is compared with conventional motor-speed control techniques, i.e., “volts-per-hertz” and “slip-frequency” control techniques.
Fig.3. Block diagram for the motor-speed control
3. COMPARISON OF THREE MOTEOR SPEED CONTROL TECHNIQUE
Comparisons among the three motor speed control techniques, with a focus on similarity and difference. The“volts-per-hertz”
control or shortly “V/f” control has two independent variables V1 and f, in which V1 is the stator voltage and f is the stator frequency. On the other hand, the two dependent variables are
the stator current I1 and the slip frequency fs. The V/f control is a straightforward speed control requiring no speed sensor, which is based on feed-forward control of V1 and f. However, both motor and DSCC may suffer from an over current during the start-up or when a rapid change in torque occurs. The slip- frequency control has two independent variables I1 and fs and the two dependent variables are V1 and f. Here, the commands for I1 and fs are determined by a feedback loop of the motor mechanical speed, thus requiring a speed sensor attached to the motor shaft. The slip-frequency control can provide a faster torque response than the V/f control because of the existence of a feedback control for the motor mechanical speed. The motor-speed control proposed for the DSCC-based induction motor drive has two independent variables I1 and f, and the two dependent variables are V1 and fs. Unlike the slip frequency control, the motor-speed control requires no speed sensor because the commands for I1 and f, i.e., I1* and f* are given not by feedback control, but by feed-forward control, as done in the V/f control. This implies that the motor speed control proposed system is inferior to the slip frequency control, in terms of torque controllability. However, it is applicable to a fan- or blower-like load, where the load torque is changing relatively slow and predictable Moreover, no over current occurs during the start-up, or when a rapid change in torque occurs, because of the existence of a feedback control loop of the stator current.
Table .1.Comparisons motor-speed control technique
Volt-per- hrertz control
Slip frequen
cy control
Propos ed motor
speed control Independ
ent variables
V
1and f I
1and f
sI
1and f
Depende nt variables
I
1and f
sV
1and f
V
1and f
Voltage control
Feedforw ard
- -
Current control
- Feedbac k
Feedba ck Speed
sensor
NO YES NO
An energy saving during a start-up does not make a significant contribution to total energy saving performance from a practical point of view because the motor power in a low speed range is negligible in applications such as fan- or blower-like loads. This means that a comparison of the three methods, in terms of energy saving performance during a
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start-up, does not make sense when fan- or blower-like loads are considered. Moreover, current stresses of the conventional motor-speed control techniques, the V/f and slip-frequency control, and the proposed motor-speed control technique are the same, at least, in a steady-state condition when a magnetizing current is set to the same value in all speed range.
3.1 Command Stator Currents
This section describes how to determine the command of the stator rms current I1∗ and the stator-current frequency f∗. The following two methods can be used to determine I1∗ and f∗: • Determination from the equivalent circuit shown in Fig.
3.4
• Determination from experiments.
3.1.1. Design Considerations
The following practical limitations should be imposed on I1∗.
• I1∗ should take the smallest current to produce a desired motor torque TM.
• The maximum value of each arm current is lower than the amplitude of the rated stator current.
The first condition should be met because as I1∗ gets larger, ΔVCju gets higher, In other words, minimizing I1∗ enables minimization of ΔVCju. The second limitation should be met because an increase in the arm currents brings additional loss to a DSCC and makes the centre-tapped inductors larger and heavier. Note that such an increase in the arm currents occurs particularly in low-speed operation, where a large amount of ac circulating current is superimposed on each arm current.
The ac circulating current superimposed results in mitigating the ac-voltage fluctuation appearing across the dc capacitor of each chopper cell. Hence, I1∗should be minimized because the ac component of the arm current is proportional to I1∗.
3.1.2. Determination from the Equivalent Circuit
When a speed-versus-load-torque characteristic is known, the equivalent circuit shown in Fig.3.4 can be used to determine I1∗ and f∗, along with the motor parameters including the moment of load inertia. The motor torque should satisfy the following equation during the start-up:
(5)
Where TL is the load torque, JM is the moment of inertia of the motor, JL is that of the load, and ωrm is the mechanical angular velocity. The right-hand term on (5) corresponds to an acceleration torque for the start up. For making analysis simple and easy, the following reasonable approximations are made.
• The stator-current frequency f agrees well with its command f ∗ (i.e., f=f∗).
• The slip frequency fs is much smaller than f.
• The moment of inertia of the load JL is much larger than that of the motor JM (i.e JM <<JL).
These three assumptions are applicable to fan- or blower-like loads for the following reasons. The first assumption is valid
because the motor frequency, or the motor mechanical speed, is adjusted slowly, e.g., spending a few or several minutes to complete its start-up procedure. The second assumption is reasonable for an induction motor. The third assumption is valid because JL is typically 50–100 times larger than JM ,Finally, simplified as follows:
(6)
Finally, I1 is obtained
(7)
4. MODEL OF THE PROPOSED START UP METHOD:
Fig 4. Model of the proposed scheme built in Simulink.
Here, a three phase 12-pulse diode rectifier, consisting of a three-winding transformer with a Δ−Δ–Y connection and two three-phase six-pulse diode rectifiers, is used as the front end.
When the supply voltage matches the motor voltage, a transformer less medium-voltage motor drive can be achieved by replacing the 12-pulse diode rectifier with a six- pulse diode rectifier. Neither electrolytic capacitor nor film capacitor is connected to the common dc link
5. SUBSYSTEMS WITH & WITHOUT SPEED SENSOR
Fig .5. subsystem without speed senssor
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Here, command voltage obtained from averaging method and command voltage obtained from balancing control is used to regulate the mean dc voltage. Motor current feedback control using feed forward method will eliminate the speed sensor from motor. Similarly we can design same block in simulation with feedback control using speed sensor as shown in below figure 3.10. If we use speed sensor then time required to set the steady speed will be less shown in results compared in next part of report. But if we use speed sensor in hostile environment like effects of radiation, underwater operation, vacuum operation, and extremely high and low temperatures then there is discontinuity of work and other things so in hostile environment we should prefer this proposed scheme with speed sensor and decoder use having some drawbacks for hostile environment
Requirement of shaft extension
Reduction of mechanical robustness of motor drive
Reduce the drive reliability
Fig 6. subsystem with speed senssor
5. RESULTS
5.1 Comparitive Result Without & With Speed Sensor
The project aimed to analyse the starting of Induction Motor Without sensor.For that Matlab simulation has been carried out and the results are copmaired with and without sensor.
Fig.7.start-up waveforms when I1*=6.4 A (20%) and TL = 0%, where I0 = 6.4 A (35%) (Without speed sensor)
Fig.8. start-up waveforms when I1∗=6.4 A (20%) and TL = 0%, where I0 = 6.4A (35%) (With speed sensor) Result shown above is for start-up performance of induction motor at stator current of 20% at no load torque. However, the maximum value of the arm currents was smaller than the amplitude of the rated stator current of 45A. The peak-to-peak ac voltage fluctuation of VC1u and VC5u was 29 V, which are 21% of 140 V.
During this performance harmonic voltage in line to line voltage can be eliminated by using low pass filter. A square- wave common-mode voltage with and square-wave circulating currents were superimposed to mitigate the ac- voltage fluctuation of each dc-capacitor voltage.
Fig.9.start-up waveforms when = 10 A (31%) and
TL = 20%, where I0=7.0 A (37%).(without speed sensor)
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Fig.10. Start-up waveforms when = 10A (31%) and
TL = 20%, where I0 = 7.0A (37%). (With speed sensor)
The above figures shows the experimental start-up performance with TL = 20%. Here, was set to 10 A (31%), which is the minimal value to produce a motor torque of 20%.
The magnetizing current I0 is 7.0 A, which is 38% of the rated magnetizing current of 18.4 A. The motor mechanical speed was increasing, where the slip frequency was fs = 0.30 Hz.
The maximum amplitude of the arm currents was 23 A, which is 51% of 45 A. The peak-to-peak ac-voltage fluctuation of VC1u and VC5u was 34 V, which is 24% of 140 V.
Fig.11. Start-up waveforms when = 17 A (53 %) and TL = 20%, where I0 = 16.6A (90%).(without speed sensor)
Fig.12. Start-up waveforms when = 17 A (53 %) and TL = 20%, where I0= 16.6 A (90%).(with speed sensor)
Above figure shows the experimental start-up performance with TL = 20%. Here, was set to 17 A (53%), the magnetizing current I0 reached 16.6 A (90%). The maximum amplitude of the arm currents was 46A, which is 101% of 45 A. The peak-to-peak ac voltage fluctuation of VC1u and VC5u was 51 V, which are 36% of 140 V.
The arm-current amplitude and the peak-to-peak ac voltage fluctuation increased by 50% and 12%, respectively,
These experimental results verified that the motor-speed control with the minimal stator current is effective in reductions of both arm-current amplitude and peak to- peak ac-voltage fluctuation.
Fig.13.Start-up waveforms when = 14 A (44%), and TL = 40%, where I0 = 9.9 A (54%). (Without speed sensor)
Fig 14. Start-up waveforms when = 14 A (44%), and TL = 40%, where I0 = 9.9 A (54%).(with speed sensor) Above figure shows the experimental start-up performance with TL = 40%. The motor mechanical speed was increasing up to 590 min−1, where the slip frequency was fs = 0.33 Hz.
The maximum amplitude of the arm currents was 34 A, which is 76% of 45 A. The peak-to-peak ac-voltage fluctuation of VC1u and VC5u was 38 V, which is 27% of 140 V.
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Fig.15.Start-up waveforms when = 17 A (53%), and TL = 60%, where I0 = 12.0 A (65%) (Without speed sensor)
Fig.16.Start-up waveforms when = 17 A (53%), and TL = 60%, where I0= 12.0A (65%). (With speed sensor) The motor mechanical speed was decreasing to 588 min−1, and the slip frequency was increasing to fs = 0.4 Hz due to the increase of TL. These experimental results show that the motor-speed control with the minimal stator current makes it possible to increase a start-up torque by a factor of three, without additional stress on arm currents and ac-voltage fluctuations
Fig.17.Steady-state waveforms when = 17A (5 3 %), f * = 1 Hz, and TL = 60%, where I0 = 12.0A (65%).(without
speed sensor)
Fig.18.Steady-state waveforms when = 17A (5 3 %), f * = 1 Hz, and TL = 60%, where I0 = 12.0A (65%).(with
speed sensor)
Above figure shows those at f* = 1 Hz. Here, the common- mode voltage with Vcom = 180 V and fcom = 50 Hz and the square wave circulating currents were superimposed. The motor mechanical speed and the slip frequency were Nrm = 19 min−1 and fs = 0.38 Hz, respectively. The maximum amplitude of the arm currents was 38 A, which is 84% of 45 A. The peak-to-peak ac-voltage fluctuation of VC1u and VC5u was 34 V, which is 24% of 140 V.
Fig.19.Steady-state waveforms when = 17A (53%),
f * = 15 Hz, and TL = 60%, where I0 = 12.0A (65%).(without speed sensor)
Above Figure shows those at = 15 Hz. Here, Vcom was reduced to 113 V, and the amplitude of the square-wave circulating currents was reduced simultaneously. The motor mechanical speed and the slip frequency were Nrm = 438 min−1 and fs = 0.4 Hz, respectively. The maximum amplitude of the arm currents was 31 A, which is 69% of 45 A. The peak-to-peak ac voltage fluctuation of VC1u and VC5u was 43 V, which are 31% of 140 V.
6. CONCLUSION
The proposed start-up method for DSCC of an induction motor drive without speed sensor is from standstill to middle speed. This start-up method is characterized by combining capacitor-voltage control and motor-speed control. The motor-speed control with the minimal stator current under a load torque is based on the combination of feedback control of the three-phase stator currents with feed forward control of
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their amplitude and frequency. The arm-current amplitudes and ac-voltage fluctuations across each of the dc capacitors can be reduced to acceptable levels.This method is suitable particularly for adjustable-speed motor drives of large- capacity fans, blowers, and compressors for energy savings.
The main objective of MMCI for starting of I.M is to study per unit rise in the speed from standstill to middle speed in the without sensor. On the other hand using the sensor there is an overshoot to the rated speed in the first quarter of the response and it is not check in the staring performance.
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