A Semi-Hexagonal Array (1×2) Antenna Using Half Mode Substrate Integrated Waveguide for
Short Range Communication Devices
Mehr E. Munir
Electrical Engineering Department Iqra National University
Peshawar, Pakistan [email protected]
Shahryar Shafique Qurashie Electrical Engineering Department
Iqra National University Peshawar, Pakistan [email protected]
Abstract—In this paper, the authors propose a single element semi-hexagonal half mode substrate integrated waveguide (HMSIW) antenna split across the line joining the opposite edge center of a hexagonal cavity, such that the line of separation includes the radiating edge, while the other edges are lined with metallic vias. The antenna was designed and fabricated on Arlon AD270 and the substrate has a gain of 5.8 dB at 5.9 GHz. The proposed array element is then used to design a linear array (1×2) resonating at 5.95 GHz. Antennas are useful applications in vehicular communication systems, serving as internal parts of dedicated short range communication devices with frequency of operation laying in the IEEE 802.11p band.
Keywords—semi-hexagonal array; short range; vehicular communication
I. INTRODUCTION
Dedicated short range communication (DSRC) is popularized worldwide as the wireless communication protocol for vehicles following Wi-Fi architecture [1] and it was initially focused on low overhead operations following IEEE 802.11a standards. However, with the advent of years and in compliance with development and modern needs to support high-speed moving vehicles and to further simplify the communication mechanisms, IEEE working group amended IEEE 802.11 standards to incorporate Wireless Access in Vehicular Environments (WAVE). WAVE formed the core of DSRC in supporting intelligent transportation systems’ (ITS) applications for short range communication. WAVE, following IEEE 802.11p standards, provides real-time traffic information, improves transportation safety, minimizes traffic congestion and helps maintaining transport sustainability. It helps establishing communication between vehicles (V2V) or between vehicles and roadside information (V2I) in the 5.9 GHz band (5.85–5.925 GHz) [2-5]. With the involvement of several companies, car manufacturers and universities worldwide pursued extensive research to develop IEEE 802.11p standard commercial products. Researchers extended their contribution in developing printed antennas and arrays to be used in conjunction with other devices for short range communication to support ITS applications [6-9].
Though hexagonal shaped substrate integrated waveguide (SIW) based components are widely popular [10-14], yet little has been reported about the unexplored domain of hexagonal SIW based antennas and arrays. As a result, in this paper, authors propose a novel semi-hexagonal HMSIW antenna operating at IEEE 802.11p frequency of 5.9 GHz and subsequently developed linear and planar arrays using the former as array elements. The 1×2 semi-hexagonal HMSIW array operates at a resonating frequency of 5.9 GHz with a gain of 8.2 dB. The antennas are designed and fabricated using Arlon AD270 substrate and the necessary full wave simulation are all carried out in ANSYS HFSS v15.0. The simulation obtained results are compared with experimentally obtained results.
II. ANTENNA DESIGN
The concept of hexagonal waveguide is further extended to a substrate integrated waveguide concept wherein the metallic walls lying along the direction of the propagation are replaced by metallic conducting vias and the whole waveguide is integrated into a dielectric filled PCB. Due to the resemblance of the hexagonal waveguide with the circular/cylindrical one, the former has been modeled in terms of its circular counterpart. The first twenty one normal modes and corresponding cut-off frequencies are all obtained for the E- modes of waveguides with regular hexagonal cross-section.
The cut-off frequency of the first mode for a hexagonal waveguide is given as the designing of antenna is achieved level by level in a appropriate way. The basic shape is shown in Figure 1[14-18].
= √ (1)
where c is the speed of light in vacuum (≈3×1010cm×s-1), kcmn, is the cut-off wave number and s is the side length of the regular hexagon. The fundamental TM01 mode is chosen as the mode of operation as it provides maximum directional radiation from the antenna. The cut-off wave number of the TM01 mode obtained after putting m=0, n=1 and kc01=2.69 is
RETRACTED
lea me num of lea the fre the
cav fre Wi len the cav the fab 5.9 oth A.
ant cha pro B.
pat
fre C.
pat
wh and
He res by of cendia res
= .
√
However a d ads to the va ethods have b mber of the h such a struct ads to the acce e designed pr equency of a f e TM01 mode
= .
√
Initially a f vity with side equency of 5.9
ith the array in ngth reduced t eoretical cut o
vity for TM01 e resonating bricated proto 9GHz are sho her dimensions
Substrate Sel Substrate sel tenna. Due t aracteristics A oposed design
Patch Width With the hel tch is calculate
=
Here εr is equency and C
Patch Length With the hel tch is calculate
= here
d
= The hexago ence, preservin sonator, we ca
bisecting the bisection lie nters and Type agonal of the spectively. W
direct approxim alue shown in been used for hexagonal wav
ture modeled eptance of the rototypes. Th full mode hex is given by
full-mode SIW e length s=15
9GHz exciting ncorporation a to 13.5mm. S off frequency 1 mode obtain frequency ob otype and the
wn in Figure s are shown in lectivity lectivity is the
o its high p Arlon AD270
[16].
lp of the follo ed [17].
the relative C is the rapidity
h
lp of the follo ed [17-18].
2∆
=
1 nal cavity is ng the TM01 an obtain two t cavity in two s along the p e-2, in which t
hexagon, as d We chose the
mation from a n [15]. The f r approximatin veguide, and a as a substrate e modified val hus the formu xagonal SIW c
W (FMSIW) 5mm was desi g the fundam along its perip ubstituting s=
of a full mo ned is 5.9GHz btained throug e fundamenta 1 (b) and (c) n Table I.
first step whe erformance a is chosen a
owing equatio
e constant w y of light in va
owing equation
/
s symmetrical 1 mode of the
types of half m o ways: Type-
plane joining the line of bise depicted in Fig Type-1 HMS
(2) circular wave fact that num ng the cutoff also, the appli
e integrated c lue as applica ula for the cu
cavity, operat
(3) regular hexa igned at the mental TM01 m
phery the actua
=13.5mm in (3 ode hexagonal z which is eq gh simulation al TM01 mo ) respectively,
en designing a and high relia as substrate fo
on, the width
(4)
with f0 functi acuum.
n, the length
(5) (6)
(7) l about two e parent hexa mode SIW ant 1, in which th the opposite ection lies alon gures 2(a) and SIW structure
eguide merical wave cation cavity, able in ut off ting in
agonal center mode.
al side 3), the l SIW qual to n. The ode at , their
patch ability or the
of the
ioning
of the
axes.
agonal tennas he line edge ng the d 2(b) e. The
HM alon dev hex Fig (tmloss mm con diam cen inse dist stru sup nec
Fig.
distr of th
Fig.
ante
L 60
MSIW based se ng the walls o void, lying al xagonal cavity gure 3. The an m) with 0.79 m
s tangent tan m(L)×60 mm(W
nsidering the c meter is 1 m nter) is 1.5 mm et feed of wid tance of L5=8 ucture to mat ppress reflect cessary dimens
(b 1. (a) Geom ribution for the pr he cavity.
2. Design of enna
TABLE I.
L 60
TABLE I.
L W h 60 0.78
emi-hexagonal of the hexagon long the line y and excited ntenna is devel mm thickness nδ=0.002 wi W). The leng corrected edge mm while the
m. To excite th dth L7=0.58 m 8.22 mm from
tch with the tion inducing sions of the an
b)
metry of the FMS rincipal TM01 m
(a) f (a) Type-1 and
DIMENSIONS OF W s 60 15 0
DIMENSIONS OF I1 I2
15 30
l antenna lined n with the rad
of bisection d with inset f
loped on Arlo s, dielectric co
ith its overa gth of each si e length, is s=1
inter-via sep he fundamenta mm is inserte m the base of t
100 Ω impe g spurious b ntenna are enlis
(a)
SIW hexagonal ca mode at 5.9GHz. (
(b d (b) Type-2 HM
F THE FMSIW HEX h I1 I2
0.78 15 15
THE FMSIW HEXA I3 I4
17 30 8.
d with metallic diating surface
of the full m feed is depicte on AD270 sub
onstant ɛr=2.7 all size being de of the ant 13.5 mm. The paration (cente al TM01 mode ed at an optim the semi-hexag dance in ord beams. The sted in Table I
(c) avity. (b) Electri (c) Fabricated pro
)
MSIW semi-hex
XAGONAL CAVITY
2 g
5 15
AGONAL CAVITY ( I5 I6
.21 1.72 0
c vias , vias mode ed in strate 7 and
g 60 tenna,
vias’
er-to- e, the mized gonal der to
other II.
c field ototype
agonal
(mm)
(mm) I7
0.56
RETRACTED
Fig Fab
Fig hex
Fig TM
TM opt nar
(a)
(b)
g. 3. (a) Geo bricated prototype
g. 4. Simulated xagonal antenna fo
g. 5. Electric M01 mode.
The simulate M01 mode of timized return rrow impedan
ometry of the e of the cavity.
d and measured for TM01 mode.
Field Distributio
ed fundament the single arr n loss value (S nce bandwidth
HMSIW semi-h
return loss value
on of the array e
tal resonating rray element i S11 parameter) of 80 MHz (
hexagonal antenn
e of the HMSIW
element at 5.9 G
g frequency fo is 5.9 GHz w
) of -28.4 dB w (5.93-5.85 GH
na. (b)
W semi-
GHz for
or the with an with a Hz) i.e.
1.36 mea ther mea retu semdist rad Fig the MH figu is 5 sim 4.8 both the
Fig.
ante
sim var d.
illufreq S21 sep Fro elem occ our elem
6% fractiona asured throug reby reflecting asured values.
urn loss (S11 v mi-hexagonal a tribution for
iation pattern gure 6. The rad
help of Hittite Hz–20 GHz) a ure it is eviden 5.8 dBi while mulated and me dBi and 4.7d h E- and H-pl
antenna is obs
(a)
(b)
6. (a) E-plan enna array elemen
III. MUTUA
Table IIII dep milar HMSIW
iations in inte The results ustrates a vari quency f for d 1=-24.26,-25.5 paration distanc om the Figure ment spacing curs as reflecte r antenna array ments have
al bandwidth gh Anritsu V g very close ag . Figure 4 dep value) for TM antenna and F the same mo n of the singl
diation pattern e HMC-T2100 and a Krytar nt that the sim e the measur easured value Bi respectivel lane are found served to have
ne and (b) H-plan nt at 5.9GHz. S: S
AL COUPLING B ELEM
picts the mutu semi-hexagon er-element spa obtained are iation plot of different value 51 and -25.79
ce d=37.42, 3 e, it is obser , a small shi ed in Table III y element, the
non radiatin
h. The same VNA is -36.1
greement betw picts the simul M01 mode for t Figure 5 reflec ode. The E-p le array elem n of the antenn 0 microwave s 9000B powe mulated E-plane
red value is 5 co-pol values ly. The cross-p d to be well be
e 89.5% radiat
ne radiation patter Simulated Results
BETWEEN TWO MENTS
ual coupling s nal antenna ar acing (center-
depicted in f S11 and S2 es of d. The 9 dB are obse 5.59 and 33.1 rved that with
ift in the res I. Owing to th lateral sides o ng PEC wal
e S11 param dB at 5.93 ween simulated
lated and mea the parent HM cts its electric plane and H-p ment is depicte na is measured signal generato er meter. From
e co-polarized 5.6 dBi while
for the H-plan polarized value elow 20-30 dB tion efficiency
rn of the single el . M: Measured Re
O SIMILAR ARRA
study between rray elements -to-center dist n Figure 7 w
1 parameters coupling valu erved for valu 8 mm respecti h change in sonating frequ he typical desi
f the adjacent lls which c
meter GHz d and asured MSIW field plane ed in d with
or (10 m the d gain e the ne are
es for Bi and
.
lement esults.
AY
n two with tance) which with ues of ues of ively.
inter- uency ign of array auses
RETRACTED
app the con tog arr val cho
Anusi hex dim wit the ant net dis int oth net wa fee
Fig diff Gre line
preciable low ereby significa nstituted with gether to an ap rays, the value lues of S21=
osen.
IV. ANTEN
Two linear ntenna-1 (1×2) ing Arlon AD xagonal anten mensions liste
th a view to n e scanning cap tenna array i twork and stribution netw to each array e her. In this c twork for po avelength (λ/4 ed to the 100 Ω
g. 7. Variation ferent inter eleme een dashed line), e), d=33.18 mm (
TABLE II.
HEXAGON d (m
37.4 35.5 33.1
TABLE III.
L1 L2
80 34
TABLE I.
W1
45
w values of m antly reducing h such elemen ppreciable ext es of d=35.59
=-25.51 dB a
NNA DESIGNIN AR
HMSIW sem ) elements ha D270 substrate nna structure a ed in Table IV
not only incre pabilities of th is done with for the mos work is design element spaced consideration, ower splitting 4) impedance Ω inset feed lin
n of S11 and S2 ent spacing d. d=
d=35.59 mm (S S11: Red solid lin
MUTUAL COUPL NAL ANTENNA EL m) f (GHz) 42 5.91 59 5.90 18 5.88
DIMENSIONS OF L3 L4
8.84 1.73
DIMENSIONS OF W2 W3
2.1 0.59
mutual coupl the total size nts as they ca tent. Here, for 9 mm≡0.7λ0
and S11=-28.
NG AND RESULT RRAY
mi-hexagonal a ave been desig e using the par as shown in F V and V. The
ease the gain b he antenna. Th the help of st optimized ned in order to
d at a distance we designed and realized transformers ne.
21 for two anten
=37.42 mm (S11 S11: Black solid l ne, S21: Red dash
LING STUDY BETW EMENTS
S11 (dB) -27.37 -28.66 -26.41
F ANTENNA-1(1×
L5 L6
3 6 6.82
F ANTENNA-1(1×
W4 W5
1.3 2.2
ling between of the antenna an be brought
r designing an with correspo .66 dB have
TS OF 1×2 LINE
array antenna gned and fabr rent HMSIW Figure 8 with arrays are des but also to im he realization power distrib
performance o feed equal p e of 0.7λ0 from d a corporate d it using qu to match the
nna array elemen : Green solid lin line, S21: Black hed line).
WEEN TWO HMSIW
S21 (dB) -24.26 -25.51 -25.79
×2 ELEMENTS)(mm L7 L8
4 44
×2 ELEMENTS)(mm W6
0.59
them a array close ntenna onding been
EAR
as, viz ricated
semi- h their
signed mprove of the bution e the power m each e feed uarter-
50 Ω
nts with ne, S21:
dashed
W SEMI-
m)
m)
(a)
(b)
Fig.
ante
to o 34.6 VNAnt 8.2d For pol imp com
des gain
)
)
8. Antenna-1 enna. (b) Fabricate
V. ANTEN
From the simu operate at 5.9
6dB while the NA is -26.6dB tenna (1×2), dBi with the r the same ante
arized gains ar provement of mparison to the
Fig. 9. Re
An HMSIW b signed at IEEE n of 5.8 dB. T
1 (1×2 array ele ed prototype
NNA DESIGNING AR
ulated results, 1GHz. The ob e correspondin B at 5.86GHz
the simulated corresponding enna, the simu re 8.1dBi and f 2.4dBi is ac e single eleme
eturn loss (S11) p
VI. CO
based semi-he E 802.11p fre This parent ant
ements) (a) Geo
G AND RESULT RRAY
the linear arra btained simula ng measure v z. In Figure 1
d E-plane co g measured v ulated and me
7.9dBi respec chieved with ent antenna.
arameters of Ante
ONCLUSION
exagonal anten quency of 5.9 tenna is used a
ometry of linear
TS OF 1×2LINEA
ays (1×2) are f ated return los value using An 11 we see tha o-polarized ga value being 8 asured H-plan ctively. Thus a the 1×2 arra
enna (1×2) array
nna is proposed 9 GHz produc
as an array ele
r array
AR
found ss is -
nritsu at for ain is .1dB.
ne co- a gain
ay in
d and cing a ement
RETRACTED
in 5.9 is o the to arrenh 1×
enh
Fig mo
Fig Sim
Un con
[1]
[2]
[3]
designing and 9 GHz and the observed that e array elemen a greater exte rays with red hancement ha 2 the corres hancement by
g. 10. Electric f de
g. 11. E-plane mulated results. M
The authors niversity for p nstruction of t
D. Jiang, L.
Standard for Vehicular Tec 2036–2040, 20 S. Eichler, “P Communicatio (VTC-2007), B IEEE Standar Vehicular Envi
d fabricating li eir various para
the presence nts reduces th ent thereby fa duced sizes.
as been succe sponding gai 2.4 and 5.4 dB
field distribution
pattern of antenn M: Measured resul
ACKNOW
would like to providing the the hardware m REFE Delgrossi, “IEE Wireless Acces chnology Confere 008
Performance Eva on Standard”, IE Baltimore, USA, p rd Committee, IE
ironments (WAV
inear and plan ameters are stu
of PEC walls he mutual coup
acilitating the The primary essfully achiev in is 8.2 dB B over the par
of Antenna-1 (1
na (1×2 antenna lts.
WLEDGEMENT
o acknowledg means and e model.
ERENCES EE 802.11p: To
ss in Vehicular ence (VTC-2008)
aluation of the EEE Vehicular T
pp. 2199–2203, 2 EEE Standard f VE)-Networking S
nar antenna arr udied extensiv on the two sid pling between
design of co objective of ved. For the B indicating rent antenna.
×2 elements) for
a array) at 5.91G
ge the Iqra Na environment fo
owards an Intern Environments”, ), Calgary, Cana
IEEE 802.11p Technology Con
007
for Wireless Acc Services, IEEE, 20
rays at vely. It des of n them mpact f gain
linear gain
r TM01
GHz. S:
ational for the
national , IEEE ada, pp.
WAVE nference
cess in 007
[4]
[5]
[6]
[7]
[8]
[9]
[10]
[11]
[12]
[13]
[14]
[15]
[16]
[17]
[18]
F. Bai, H.
communication Transportation September 17–2 A. Vinel, “3GP is able to supp Wireless Comm J. Hirokawa, M for plane TEM Antennas and P H. Uchimura, T waveguide”, IE Vol. 46, pp. 243 D. Deslandes, K circuits and w Theory and Tec F. Xu, K. Wu, integrated wave Techniques, Vo D Deslandes, K considerations o on Microwave 2006 L. Yan, W. Ho
experiment on S Components Le D. Deslandes, concept and des Proceedings (A G. Q. Luo, Z. F by substrate int Propagation Let J. C. Bohorquez Pena, H. F. Gu backed antenna 8, pp. 1139-114 M. H. Awida, cavity-backed 2 Wireless Propag H. Wang, D. G.
integrated wave on Antennas an Q. Lai, C. Fum propagation pro IEEE Transacti 8, pp. 1996-200 J. Xu, W. Ho integrated wav wave applicatio Vol. 7, pp. 85-8
Krishnan, “Reli n for vehicle s Systems Confe 20, 2006 PP LTE versus IE
port cooperative munication Letters M. Ando, “Single-l wave excitation i Pr opagation, Vol.
T. Takenoshita, M EEE Transactions
38-2443, 1998 K. Wu, “Single-s waveguide filters chniques Vol. 51, , “Guided-wave a eguide”, IEEE T ol. 53, NO.1, pp. 6 K. Wu, “Accurate of a substrate int Theory and Tech
ong, G. Hua, J. C SIW slot array an etters, Vol. 14, No
“Substrate integ sign consideration APMC-2005), Suzh F. Hu, X. L. Dong tegrated waveguid tters, Vol. 7, pp. 2 z, H. A. F. Pedraz uarnizo, “Planar a”, IEEE Antenna 42, 2009
A. E. Fathy, “S 2×2 microstrip pa gation Letters, Vo . Fang, B. Zhang, eguide (SIW) – p nd Propagation, V meaux, W. Hong, operties of the hal ions on Microwav 04, 2009 ong, H. Tang, Z veguide (HMSIW
ons”, IEEE Ante 88, 2008
iability analysis safety applicatio
rence (ITSC-200
EEE 802.11p/WA vehicular safety s, Vol. 1, No. 2, p layer feed wavegu in parallel plates”
46, No. 5, pp. 62 M. Fujii, “Devel on Microwave T
substrate integrati s”, IEEE Transa No. 2, pp. 593-59 and leakage char Transactions on M
66-73, 2005 modeling, wave m tegrated waveguid hniques, Vol. 54,
Chen, K. Wu, T.
ntennas”, IEEE M o. 9, pp. 446-448, grated waveguide ns”, Asia-Pacific hou, China, pp. 3 g, L. L. Sun, “Pla de cavity”, IEEE 236-239, 2008 za, I. C. H. Pinzo
substrate integra as and Wireless Pr
ubstrate integrate atch array antenn ol. 8, pp. 1054-10 , W. Q. Che, “Die plane horn antenn Vol. 58, No. 3, pp.
R. Vahldieck, “ lf-mode substrate ve Theory and Te
Z. Kuai, K. Wu, W) leaky-wave a
nnas and Wirele
of DSRC w ns”, IEEE Inte 06), Toronto, C
AVE: which techn y applications?”, pp. 125–128, 2012
uide consisting o
”, IEEE Transacti 25-630, 1998
lopment of a lam Theory and Techn
ion technique of actions on Micr
96, 2003 racteristics of sub Microwave Theor
mechanisms and de”, IEEE Transa No. 6, pp. 2516
J. Cui,”Simulatio Microwave and W
, 2004
e leaky wave an Microwave Conf 46-349, 2005 anar slot antenna b
Antennas and W
on, J. A. Castiblan ated waveguide c ropagation Letter
ed waveguide Ku a”, IEEE Antenn 056, 2009
electric loaded sub nas”, IEEE Transa
640-647, 2010
“Characterization integrated waveg echniques, Vol. 5
“Half-mode sub antenna for mill
ss Propagation L wireless
elligent Canada,
nology IEEE 2
f posts ons on
minated niques,
planar rowave
ubstrate ry and
design actions 6-2526,
on and Wireless
ntenna:
ference
backed Wireless
nco, N.
cavity- rs, Vol.
u-band nas and
ubstrate actions
of the guide”, 57, No.
ubstrate limeter Letters,
